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Patent Analysis of

Digital AC/DC power converter

Updated Time 12 June 2019

Patent Registration Data

Publication Number

US10003254

Application Number

US15/874884

Application Date

19 January 2018

Publication Date

19 June 2018

Current Assignee

DIGITAL POWER COMPANY LIMITED

Original Assignee (Applicant)

DIGITAL POWER COMPANY LIMITED

International Classification

H02M3/335,H02M1/42,H02M7/217,H02M1/00

Cooperative Classification

H02M1/4225,H02M1/4258,H02M3/33515,H02M7/2176,H02M2001/007

Inventor

WANG, CALVIN SHIE-NING,HUANG, ZHEN QIU

Patent Images

This patent contains figures and images illustrating the invention and its embodiment.

US10003254 Digital AC/DC power converter 1 US10003254 Digital AC/DC power converter 2 US10003254 Digital AC/DC power converter 3
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Abstract

A digital AC/DC power converter comprises an active PFC module, a single switch module having a single switch, a power output module having a transformer, a digital control module having a microcontroller, and a rectifying and filtering module having a full-bridge rectifier, an EMI filter, and a capacitor that is less than 1 μF. The single switch is electrically connected to the active PFC module, and a primary winding of the transformer is electrically connected to the active PFC module. The microcontroller provides a PWM signal to control the switching state of the single switch, so that the active PFC module transforms AC frequency from less than 300 Hz into over 30,000 Hz and outputs a rectified AC voltage waveform. The EMI filter blocks high electromagnetic frequencies and the capacitor smooths a variation in the rectified voltage waveform and output the smoothed rectified voltage waveform to the active PFC module.

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Claims

1. A digital AC/DC power converter, comprising: an active PFC module; a single switch module having a single switch, wherein the single switch is electrically connected to the active PFC module; a power output module comprising a transformer, the transformer having a primary winding, wherein the primary winding of the transformer is electrically connected to the active PFC module; a digital control module having a microcontroller and electrically connected to the single switch module, wherein the microcontroller provides PWM signals to control the switching state of the single switch module, so that the active PFC module transforms an AC frequency from no more than 300 Hz into at least 30,000 Hz and outputs a rectified AC output voltage waveform to improve power factor; anda rectifying and filtering module electrically connected between an AC power source and the active PFC module, the rectifying and filtering module comprising: a full-bridge rectifier; an EMI filter; and a capacitor that is less than 1 μF; the EMI filter being electronically connected between the full-bridge rectifier and the capacitor, and the capacitor being connected to the active PFC module, wherein the full-bridge rectifier is configured to turn an AC input from an AC power source into a rectified voltage waveform, the EMI filter is configured to block high electromagnetic frequencies and the capacitor is configured to smooth a variation in the rectified voltage waveform from the full-bridge rectifier and output the smoothed rectified voltage waveform to the active PFC module.

2. The digital AC/DC power converter of claim 1, wherein the rectifying and filtering module provides a start-up signal to the digital control module to start the digital AC/DC power converter.

3. The digital AC/DC power converter of claim 1, wherein the microcontroller is an at least 8-bit microprocessor that expands at least 64 times the precision of a duty cycle of the PWM signal.

4. The digital AC/DC power converter of claim 3, wherein digital control module further comprises an auxiliary integrated circuit, and the microprocessor provides the PWM signal to the auxiliary integrated circuit so that the auxiliary integrated circuit amplifies the PWM signal and provides an amplified PWM signal to the single switch module to control the switching state of the single switch.

5. The digital AC/DC power converter of claim 3, wherein the power output module further comprises a transient voltage suppressor and a freewheeling diode, and the transient voltage suppressor and the freewheeling diode are electrically connected to the primary winding of the transformer and are used to dissipate the heat and eliminate instant high-frequency pulses.

6. The digital AC/DC power converter of claim 3, wherein the power output module further comprises a secondary winding to provide a working voltage to the digital output module.

7. The digital AC/DC power converter of claim 3, wherein the power output module provides a wake-up signal to the digital control module to wake up the digital AC/DC power converter.

8. The digital AC/DC power converter of claim 3, wherein the active PFC module further comprises a boost circuit and a π type filter, and the boost circuit controls the energy output to the π type filter based on the switching of the single switch module.

9. The digital AC/DC power converter of claim 3, wherein the active PFC module further comprises a voltage divider that provides an internal voltage of the digital power converter to the digital control module, so that the digital control module controls the duty cycle of the PWM signal based on the internal voltage.

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Claim Tree

  • 1
    1. A digital AC/DC power converter, comprising:
    • an active PFC module
    • a single switch module having a single switch, wherein the single switch is electrically connected to the active PFC module
    • a power output module comprising a transformer, the transformer having a primary winding, wherein the primary winding of the transformer is electrically connected to the active PFC module
    • a digital control module having a microcontroller and electrically connected to the single switch module, wherein the microcontroller provides PWM signals to control the switching state of the single switch module, so that the active PFC module transforms an AC frequency from no more than 300 Hz into at least 30,000 Hz and outputs a rectified AC output voltage waveform to improve power factor
    • anda rectifying and filtering module electrically connected between an AC power source and the active PFC module, the rectifying and filtering module comprising: a full-bridge rectifier
    • an EMI filter
    • and a capacitor that is less than 1 μF
    • the EMI filter being electronically connected between the full-bridge rectifier and the capacitor, and the capacitor being connected to the active PFC module, wherein the full-bridge rectifier is configured to turn an AC input from an AC power source into a rectified voltage waveform, the EMI filter is configured to block high electromagnetic frequencies and the capacitor is configured to smooth a variation in the rectified voltage waveform from the full-bridge rectifier and output the smoothed rectified voltage waveform to the active PFC module.
    • 2. The digital AC/DC power converter of claim 1, wherein
      • the rectifying and filtering module provides a start-up signal to the digital control module to start the digital AC/DC power converter.
    • 3. The digital AC/DC power converter of claim 1, wherein
      • the microcontroller is an at least 8-bit microprocessor that expands at least 64 times the precision of a duty cycle of the PWM signal.
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Description

FIELD OF THE INVENTION

The present invention relates generally to the design of a digital AC/DC power converter. More particularly, the present invention relates to utilizing a digital microcontroller to design a novel AC/DC power converter, so that the power factor (PF) of the AC/DC power converter is effectively improved.

BACKGROUND OF THE INVENTION

Power factor in power converters is defined as the ratio of the real power delivered to a load to the apparent power provided by a power source, and power converters should be able to deliver power from the power source to the load with high power factor.

Recently, government agencies gradually require power factors in power converters to exceed a certain minimum level by regulation. For example, Energy Star in U.S. requires power factors in power converter to achieve at least 87% if a specification of a device requires more than 49 W, such as notebooks. On the other hand, Energy Star in U.S. requires power factors in power converter to achieve no less than 68% if a specification of a device requires no more than 5 W, such as mobile phones.

Typically, power factor correction (PFC) is achieved through the use of specific analog integrated circuits (IC) especially designed for improving PFC in power converters. In addition, each of the aforementioned analog ICs varies in different application fields, thus lacking a generalized structure to adopt different designs in different application field.

For now, if a device requires more than 60 W, the function of PFC is usually achieved through the use of the aforementioned analog ICs in power converters. However, if a device requires no more than 65 W, the device usually does not have PFC function, since the price of power converters having the aforementioned analog ICs for improving PFC will be about or at least twice the price of power converters without PFC function.

In addition, the implementation of aforementioned conventional power converters usually requires complex circuitry further requiring considerable efforts to stabilize them. And once again, in different applications the power converters need to utilize different specific analog ICs to achieve high power factor correction.

In view of the above, there is a need for a power converter with non-complex circuitry that utilizes a common digital microcontroller that provides high PFC, and the digital microcontroller provides pulse width modulation (PWM) signal to control the power converter. The aforementioned digital microcontroller providing PWM signal is able to be regarded as a digital PWM controller.

BRIEF SUMMARY OF THE INVENTION

The invention provides a digital AC/DC power converter with a single switch working with a microcontroller to improve power factor. Specifically, the microcontroller is implemented by an at least 8-bit (such as 16-bit, 32-bit . . . etc) microprocessor so that the precision of duty cycle of a PWM signal generated from the microprocessor is expanded.

In one embodiment, a digital AC/DC power converter comprises an active PFC module, a single switch module, a power output module, a digital control module, and a rectifying and filtering module. The single switch module has a single switch electrically connected to the active PFC module. The power output module has a transformer, and a primary winding of the transformer is electrically connected to the active PFC module. The digital control module has a microcontroller that provides a PWM signal to control the switching state of the single switch, so that the active PFC module transforms an AC frequency from no more than 300 Hz into at least 30,000 Hz and outputs a rectified AC output voltage waveform to improve power factor. The rectifying and filtering module is electrically connected between an AC power source and the active PFC module, and has a full-bridge rectifier, an EMI filter; and a capacitor that is less than 1 μF. The EMI filter is electronically connected between the full-bridge rectifier and the capacitor, and the capacitor is connected to the active PFC module. The full-bridge rectifier is configured to turn an AC input from an AC power source into a rectified voltage waveform. The EMI filter is configured to block high electromagnetic frequencies, and the capacitor is configured to smooth a variation in the rectified voltage waveform from the full-bridge rectifier and output the smoothed rectified voltage waveform to the active PFC module.

It should be understood, however, that this summary may not contain all aspects and embodiments of the present invention, that this summary is not meant to be limiting or restrictive in any manner, and that the invention as disclosed herein will be understood by one of ordinary skill in the art to encompass obvious improvements and modifications thereto.

BRIEF DESCRIPTION OF THE DRAWINGS

The accompanying drawings illustrate one or more embodiments of the invention and together with the written description, serve to explain the principles of the invention. Wherever possible, the same reference numbers are used throughout the drawings to refer to the same or like elements of an embodiment, and wherein:

FIG. 1 is a comparison plot showing the difference between an analog PWM controller and a digital PWM controller.

FIG. 2 is a block diagram of a low-power digital AC/DC power converter according to one embodiment of the present invention;

FIG. 3 is a schematic diagram of a low-power digital AC/DC power converter according to the embodiment of the present invention;

FIG. 4 is a block diagram of the middle/high-power digital AC/DC power converter according to another embodiment of the present invention:

FIG. 5 is a schematic diagram of the middle-power digital AC/DC power converter according to the embodiment of the present invention:

FIG. 6 is a schematic diagram of the high-power digital AC/DC power converter according to the embodiment of the present invention;

FIG. 7 is a soft-switching timing diagram of the middle-power digital AC/DC power converter according to the embodiment of the present invention;

FIG. 8 is a soft-switching timing diagram of the high-power digital AC/DC power converter according to the embodiment of the present invention.

In accordance with common practice, the various described features are not drawn to scale and are drawn to emphasize features relevant to the present disclosure. Like reference characters denote like elements throughout the figures and text.

DETAILED DESCRIPTION OF THE INVENTION

The present invention will now be described more fully hereinafter with reference to the accompanying drawings, in which exemplary embodiments of the invention are shown. This invention may, however, be embodied in many different forms and should not be construed as limited to the embodiments set forth herein. Rather, these embodiments are provided so that this disclosure will be thorough and complete, and will fully convey the scope of the invention to those skilled in the art. Like reference numerals refer to like elements throughout.

The terminology used herein is for the purpose of describing particular embodiments only and is not intended to be limiting of the invention. As used herein, the singular forms “a”, “an” and “the” are intended to include the plural forms as well, unless the context clearly indicates otherwise. It will be further understood that the terms “comprises” and/or “comprising,” or “includes” and/or “including” or “has” and/or “having” when used herein, specify the presence of stated features, regions, integers, steps, operations, elements, and/or components, but do not preclude the presence or addition of one or more other features, regions, integers, steps, operations, elements, components, and/or groups thereof.

It will be understood that the term “and/or” includes any and all combinations of one or more of the associated listed items. It will also be understood that, although the terms first, second, third etc. may be used herein to describe various elements, components, regions, parts and/or sections, these elements, components, regions, parts and/or sections should not be limited by these terms. These terms are only used to distinguish one element, component, region, part or section from another element, component, region, layer or section. Thus, a first element, component, region, part or section discussed below could be termed a second element, component, region, layer or section without departing from the teachings of the present invention.

Unless otherwise defined, all terms (including technical and scientific terms) used herein have the same meaning as commonly understood by one of ordinary skill in the art to which this invention belongs. It will be further understood that terms, such as those defined in commonly used dictionaries, should be interpreted as having a meaning that is consistent with their meaning in the context of the relevant art and the present disclosure, and will not be interpreted in an idealized or overly formal sense unless expressly so defined herein.

The description will be made as to the embodiments of the present invention in conjunction with the accompanying drawings in FIGS. 1˜8. Reference will be made to the drawing figures to describe the present invention in detail, wherein depicted elements are not necessarily shown to scale and wherein like or similar elements are designated by same or similar reference numeral through the several views and same or similar terminology.

FIG. 1 is a comparison plot showing the difference between an analog PWM controller and a digital PWM controller. Referring to FIG. 1, an analog PWM controller 101 generally has an error comparison unit 103, a calculation comparison unit 105, a ramp generator 107, a latch unit 109, and a driver unit 111. In addition, a power converter generally is able to have the analog PWM controller 101, a switch module 113, and auxiliary circuits 115 and 117.

The error comparison unit 103 has an amplifier and thus has a positive end to receive a reference voltage and a negative end to receive a feedback voltage that is provided from the auxiliary circuit 115. If the feedback voltage is higher than the reference voltage, the error will not be corrected. The feedback voltage is formed from a voltage divider having resistors R101 and R102 in the auxiliary circuits 115, and the auxiliary circuits 115 have a capacitor C101 and a resistor R103 to form a R-C circuit, thus providing a oscillation average value of an output waveform to the error comparison unit 103.

The calculation comparison unit 105 has an amplifier and thus has a positive end to receive an output signal from the ramp generator 107 and a negative end to receive an integrated signal that is formed by an output signal from the error comparison unit 103 and by an output signal from the auxiliary circuit 117. The auxiliary circuit 117 is a R-C circuit and receives the output signal from the auxiliary circuit 115 as well.

The calculation comparison unit 105 utilizes comparison method to obtain the variation of the pulse width and output a variable width pulse signal that is similar to a rectangular waveform. Then, to amplify the variable width pulse signal, the latch unit 109 receives the variable width pulse signal and output a variable width rectangular pulse to the driver unit 111. Typically, the output signal from the driver unit 111 is an amplified variable width rectangular pulse and its voltage needs to be higher than 5V so as to appropriately drive the switch module 113. The switch module 113 has at least one switch component, such as a MOSFET or an IGBT, and controls the DC output of the power converter.

On the other hand, referring to FIG. 1, a digital PWM controller 131 generally has a power management unit 133, a controller interface 135, a digital reference voltage unit 137, a A/D converter 139 (ADC), a digital adder 141, a digital PID filter 143, a digital PWM unit 145. In addition, a power converter generally is able to have the digital PWM controller 131, a driver unit 147, a switch module 149, and an auxiliary circuit 151.

The control interface 135 has a SDA interface for data communication and has a SCL interface for time/frequency communication. Thus, the digital reference voltage unit 137 is able to receive the signal from the power management unit 133 and the signal from the control interface 135, thus outputting a digital reference voltage to the digital adder 141. The digital adder 141 receives the signal from the ADC 139 and the signal from the digital reference voltage unit 137. The ADC 139 is able to convert an analog amount into a digital amount. For example, an analog IV signal is able to be converted to a 0˜255 digital signal by the ADC 139, wherein digital 0 represents 0V and digital 255 represents IV. In addition, the ADC 139 receives a divided voltage formed by the resistors R105, R106 in the auxiliary circuit 151.

After calculation from the digital adder 141, the digital adder 141 outputs a signal to the digital PID filter 143, and the digital PID filter 143 outputs a variable width pulse signal that is similar to a rectangular waveform. Then, to amplify the variable width pulse signal, the digital PWM unit 145 receives the variable width pulse signal and output a variable width rectangular pulse to the driver unit 147, so that the driver unit 147 is able to appropriately drive the switch module 149. The switch module 149 has at least one switch component, such as a MOSFET or an IGBT, and controls the DC output of the power converter. Hence, if the power converter adopts a digital PWM controller 131, the power converter is able to be called a digital power converter.

Compared with the power converter having the analog PWM controller, the power converter having the digital PWM controller is advantageous in the following aspects: multiple interfaces/pins to proceed A/D conversion, multiple sampling and central control, flexibility, better complex control such as intelligent control or high-precision control, and overall costs.

FIG. 2 is a block diagram of a low-power digital AC/DC power converter according to one embodiment of the present invention. Referring to FIG. 2, a digital power converter has a rectifying and filtering module 201, an active PFC module 203, a single switch module 205, a power output module 207, and a digital control module 209.

In, FIG. 2, the power transmission direction is from an AC input to a DC output sequentially via the rectifying and filtering module 201, the active PFC module 203, and the power output module 207.

The rectifying and filtering module 201 is electrically connected to the AC input, the active PFC module 203, and the digital control module 209. The active PFC module 203 is electrically connected to the rectifying and filtering module 201, the power output module 207, and the digital control module 209. The power output module 207 is electrically connected to the DC output, the active PFC module 203, and the digital control module 209. The single switch module 205 is electrically connected to the active PFC module 203 and the digital control module 209.

The digital control module 209 provides an amplified PWM signal Spwm to the single switch module 205 to control the ON/OFF switching state so that the single switch module 205 is able to output a digital PWM signal to the active PFC module 203. In addition, the single switch module 205 provides a feedback signal Iproduct to control the output of the amplified PWM signal Spwm, thus preventing potential damage of a single switch in the single switch module 205.

The rectifying and filtering module 201 provides a start-up signal to the digital control module 209 to start the digital AC/DC power converter. The power output module 207 provides a wake-up signal to the digital control module 209 to wake up the digital AC/DC power converter. In addition, the active PFC module 203 provides an internal voltage of the digital power converter as a feedback signal to the digital control module 209, so that the digital control module 209 detects the internal voltage and is able to control the duty cycle of the amplified PWM signal Spwm.

FIG. 3 is a schematic diagram of the low-power digital AC/DC power converter that illustrates more details of FIG. 2 according to one embodiment of the present invention. Referring to FIG. 3, the rectifying and filtering module 201 has a voltage dependent resistor (VDR) R300, a fuse S301, a full-bridge rectifier BR1, an electromagnetic interference (EMI) filter EF, capacitors C300 and C301, and a start-up signal line 301. It should be noticed that the rectifying and filtering module 201 is connected to an AC power source for the AC input.

Typically, the frequency of the AC input is 50˜60 Hz and the AC input is electrically connected to the voltage dependent resistor R300 and the fuse S301. The voltage dependent resistor R300 is used to provide over-voltage protection, and the fuse S301 is used to provide over-current protection. The full-bridge rectifier BR1 makes use of four diodes in a bridge arrangement to achieve full-wave rectification that turns the AC input into a rectified voltage waveform. The EMI filter EF is used to block high electromagnetic frequencies that are recognized as noises.

The capacitor C301 is used to smooth the variation in the rectified voltage waveform from full-bridge rectifier BR1. However, the capacity of the capacitor C301 is selected to be less than 1 μF and better ranges from 200 nF to 300 nF, thus merely filling a small part of the valley in the rectified voltage waveform and preventing low PFC caused by large C301 capacity.

To decrease the power consumption of the standby state of the digital power converter, the start-up signal line 301 is responsible for transmitting the start-up signal and obtaining the signal from a half bridge of the full-bridge rectifier BR1. Thus, the signal coming from a node N0 is a half-wave rectified signal and is filtered by the capacitor C300. The filtered signal in the start-up signal line 301 is provided to an auxiliary IC 303. While the digital power converter is electrically connected to the AC input, a start-up current is immediately formed and is transmitted from the node N0 to the auxiliary IC 303 via the start-up signal line 301, thus enabling the digital power converter to work.

In FIG. 3, the active PFC module 203 has a boost circuit formed by an inductor L301, a diode D301 and a diode D302, a π type filter formed by an inductor L302, a capacitor C302 and a capacitor C303, and a voltage divider formed by resistors R301, R302 and R303.

In the active PFC module 203, the diode D302 can be regarded as a switch electrically connected to a power MOSFET P301 in the single switch module 205, and the diode D302 is controlled by the digital control module 209 electrically connected with the power MOSFET P301. When the diode D302 is switched to an ON state, the voltage of the left side of the inductor L301 is higher than that of the right side of the inductor L301, thus storing energy in a magnetic core surrounding by the inductor L301. When the diode D302 is switched to an OFF state, the voltage of the left side of the inductor L301 is lower than that of the right side of the inductor L301, thus releasing energy in the magnetic core through the inductor L301. In addition, the diodes D301 and D302 may be high-frequency diodes.

In the active PFC module 203, when the diode D301 is turned on, the voltage of the left side of the diode D301 is higher than that of the right side of the diode D301, thus storing the energy from the boost circuit to the capacitors C302 and C303.

Basically, the energy stored in the capacitors C302 and C303 is used to fill a large part of the valley in the rectified voltage waveform. It should be noticed that the rectified voltage waveform can be regarded as a low-frequency envelope of a high-frequency waveform created by the amplified PWM signal Spwm provided by the digital control module 209 since the amplified PWM signal Spwm turns the frequency below 300 Hz into at least 30,000 Hz by controlling the switch state of the diode D302, wherein the frequency below 300 Hz is the frequency of AC input. For example, the frequency of the amplified PWM signal may be 60,000 Hz. Therefore, the switching of the diode D302 turns the low-frequency state of the rectified voltage waveform into a high-frequency state, thus creating the rectified AC output voltage waveform with high-frequency.

The voltage divider formed by resistors R301, R302 and R303 is used for a microcontroller 305 in the digital control module 209 to detect the internal voltage of the digital power converter. When the microcontroller 305 determines the power MOSFET P301 not to work, the internal voltage is able to be proportional to input voltage from the AC power source. When the microcontroller 305 determines the power MOSFET P301 to work, the detected voltage is able to be proportional to the voltage boosted by the boost circuit.

For example, when the power MOSFET P301 is working, the microcontroller 305 is able to detect the peak voltage boosted by the boost circuit. If the peak voltage is higher than a specific threshold, the duty cycle of the switching of the power MOSFET P301 will be adjusted by the microcontroller 305. The resistance value of the resistors R1 and R2 is able to be range from 105 to 107Ω, and the resistors R301 and R302 need to endure at least 440V.

In FIG. 3, the single switch module 205 has the power MOSFET P301 and resistors R304, R305 and R306, and the power MOSFET P301 can be regarded as a single switch. The resistor R304 is electrically connected to the source end of the power MOSFET P301 and is also electrically connected to the auxiliary IC 303. In addition, the resistor R304 is used to sample the current passing through the source end of the power MOSFET P301. If the current passing through the source end is larger than a specific threshold, the digital control module 205 will not output the amplified PWM signal or will decrease the amplified PWM signal, thus protecting the power MOSFET P301.

The resistor R305 is electrically connected to the gate end of the power MOSFET P301 and is also electrically connected to the auxiliary IC 303 in the digital control module 205. In addition, the resistor R305 is used to transmit the amplified PWM signal Spwm provided by the digital control module 209. The resistor R306 is electrically connected to the gate end of the power MOSFET P301 and is also connected to the ground, thus preventing erroneous trigger of the power MOSFET P301.

In FIG. 3, the power output module 207 has a transient voltage suppressor (TVS) D303, a freewheeling diode (FWD) D304, a transformer TR having a primary winding Np, a 1st secondary winding Ns1 and a 2nd secondary winding Ns2, and a optical coupling circuit formed by an inductor L303, resistors R308, R309 and R310, an optical coupler OC1, an diode D306, and a capacitor C308. In addition, the 1st secondary winding Ns1 is electrically connected to a diode D305, a R-C circuit having a resistor R307 and a capacitor C304, and capacitors C305, C306 and C307. Moreover, the 2nd secondary winding NS2 is electrically connected to a diode D307 and a capacitor C310. It should be noticed that the power output module 207 further contains a capacitor C309 and is connected to a DC load for the DC output.

The transient voltage suppressor (TVS) D303 and the freewheeling diode (FWD) D304 form an absorption circuit. When the power MOSFET P301 is switched to an ON state, a magnetic core surrounding by the primary side of the transformer TR stores energy passed from the active PFC module 203. When the power MOSFET P301 is switched to an OFF state, the magnetic core surrounding by the primary side of the transformer TR releases energy passed from the active PFC module 203, and thus the transient voltage suppressor D303 and the freewheeling diode D304 absorb the energy and inverse the direction of the magnetic field lines of the magnetic core surrounding by the primary side. Due to the aforementioned energy absorption, the transient voltage suppressor D303 and the freewheeling diode D304 dissipate the heat and eliminate instant high-frequency pulses.

The transformer TR is used to transform the voltage from the active PFC module 203 and provide isolation between the AC input and the DC output. The diode D305 is used to provide rectification for the signal outputted from the 1st secondary winding Ns1. The R-C circuit having the resistor R307 and the capacitor C304 is used to absorb high-frequency pulses, and the capacitors C305, C306 and C307 is used for filtering, thus decreasing ripples of the signal outputted from the 1st secondary winding Ns1. In addition, the 2nd secondary winding Ns2 is used for providing a working voltage to the digital control module 209, so that all the components in the digital module 209 operate normally. For example, the auxiliary IC 303 is able to receive the working voltage provided by the 2nd secondary winding Ns2, wherein the working voltage is able to range from 4˜5V.

The optical coupling circuit formed by the inductor L303, the resistors R308, R309 and R310, the optical coupler OC301, the diode D306, and the capacitor C308. The resistors R308 and R309 are used for voltage limitation, and the resistors R309 and R310 forms a voltage divider. The diode D306 is used for precise voltage regulation. If the voltage provided by the voltage divider formed by the resistors R309 and R310 is higher than a specific threshold, the diode D306 will be switched to an ON state. On the other hand, if the voltage provided by the voltage divider formed by the resistors R309 and R310 is lower than the specific threshold, the diode D306 will be switched to an ON state. Hence, the diode D306 decides whether the optical coupler OC301 generates lights. If the voltage between the resistor R308 and the diode D306 is higher than a specific threshold, the optical coupler OC301 generates lights, thus providing a feedback signal proportional to the output voltage to a microcontroller 305.

In FIG. 3, the digital control module 209 has the microcontroller 305, the auxiliary IC 303, and an optical coupling circuit formed by an optical coupler OC302, resistors R311 and R312, and a capacitor C313.

The auxiliary IC 303 can be regarded as a power management and driver IC. The auxiliary IC 303 has Pin 1 to sense the start-up signal, Pin 2 to sense the gate current of the power MOSFET P301, Pin 3 to provide the amplified PWM signal to the power MOSFET P1 for switching control, Pin 4 to obtain the working voltage from the 2nd secondary winding Ns2, Pin 5 to receive an original PWM signal from the microcontroller 305, Pin 6 to communicate with the microcontroller 305, and Pin 7 to provide voltage for the microcontroller 305 to work. In addition, the communication via Pin 6 can be bi-directional and includes the function of detecting error signal of the auxiliary IC 303, confirming whether the auxiliary IC 303 is in a normal working mode.

On the other hand, the microcontroller 305 has Pin 8 to receive the working voltage provided from the auxiliary IC 303 to make it works, Pin 9 to communicate with the auxiliary IC 303, Pin 10 to provide the PWM signal to the auxiliary IC 303, Pin 11 to detect the internal voltage of the digital power converter, Pin 12 to connect the ground, Pin 13 reserved for other use, Pin 14 to receive a wake-up signal from the digital output module 207, and Pin 15 to receive a signal representing the output voltage from the optical coupling circuit of the digital control module 209.

In addition, the wake-up signal is transmitted via a wake-up signal line 307 that is designed for stand-by power mode. When the load connected with the DC output is in a system-off state, the design of the stand-by power in the digital power converter is able to save the power consumption of the load, reducing the original 1˜3 W power consumption to no more than 100 mW power consumption. Thus, if the voltage of the DC output has a small variation, such as 100 mV variation caused by the plug-in of an USB, the microcontroller 305 will be waked up by the wake-up signal.

Due to the design of the power output module 207, the digital AC/DC power converter in FIG. 3 can be regarded as a fly-back type power converter.

FIG. 4 is a block diagram of the middle/high-power AC/DC digital power converter according to another embodiment of the present invention. Referring to FIG. 4, a digital power converter has a rectifying and filtering module 401, an active PFC module 403, a single switch module 405, a power output module 407, and a digital control module 409. The main difference between FIG. 2 and FIG. 4 is that the digital control module 409 provides additional control signal Sswitch to the power output module 407, thus creating a smart control scheme to fulfill the design of quasi-resonant soft switching in a zero voltage switch (ZVS) way and thus achieving the power conversion of middle/high power application. For example, the middle power application refers to the application utilizing power ranging from 80˜200 W, and the high power application refers to the application utilizing power ranging no less than 200 W.

FIG. 5 is a schematic diagram of the middle-power digital AC/DC power converter according to the embodiment of the present invention. The main difference between FIG. 5 and FIG. 3 is that the implementation of the power output module 407 in FIG. 5 is different from that of the power output module 207 in FIG. 3.

Referring to FIG. 5, the power output module 407 includes two switches M501 and M502 in series connection to ground. A microcontroller 505 controls an auxiliary IC 503 to output different rectangular pulses via Pin A1 and Pin A2, so that the switch M502 maintains in an OFF state when the switch M501 is switched to an ON state, and the switch M501 maintains in an OFF state when the switch M502 is switched to an ON state. Therefore, two switches M501 and M502 operate alternatively in an opposite working state. In addition, the switches M501 and M502 may not both operate in the ON state due to the connection to ground. Preferably, the switches M501 and M502 may be MOSFET.

In the aforementioned power output module 407, a transformer TR includes a primary winding Np, a 1st secondary winding Ns1 and a 2nd secondary winding Ns2. The left side of the primary winding Np is electrically connected to the switches M501 and M502, and the right side of the primary winding Np is electrically connected to two capacitors C504 and C505.

When the switch M501 is in an ON state and the switch M502 is in an OFF state, the primary winding Np obtains energy from the capacitors C504 and C505. Meanwhile, the voltage in the left side of the primary winding Np is higher than and twice the voltage in the right side of the primary winding Np, and the magnetic core surrounding by the primary side of the transformer TR stores energy.

When the switch M501 is in the ON state and the switch M502 is in the OFF state, if the switch M501 is switched to an OFF state, the voltage in the left side of the primary winding Np will be changed to be lower than and half the voltage in the right side of the primary winding Np. In this situation, both of the switch M501 and the switch M502 are in the OFF state.

When the switch M501 is in the OFF state and the switch M502 is in the OFF state, if the switch M502 is switched to an ON state, the voltage in the left side of the primary winding Np will be changed to zero voltage and thus lower than the voltage in the right side of the primary winding Np, thus changing the direction of saving energy in the magnetic core of the transformer TR. Since the direction of magnetic lines inverses immediately in the aforementioned situation, the magnetic core is not easy to saturate, thus improving working efficiency, the operation rate of the magnetic core and the conversion rate of energy.

Then, when the switch M501 is in the OFF state and the switch M502 is in the ON state, if the switch M502 is switched to an OFF state, the switch M501 will be prepared to switch to an ON state after the switching of the switch M502. Therefore, a complete control cycle is achieved through the aforementioned switching process of M501 and M502 in FIG. 7. Therefore, the next start of the control cycle is to make the switch M501 be switched to an ON state, so that the switch M501 is in an ON state and the switch M502 is in an OFF state.

In addition, the power output module 407 has two inductors L503 and L504. The inductor L503 is used to store and release redundant energy, and the inductor L504 is used to achieve filtering with a nearby magnetic core. Furthermore, the power output module 407 has a sampling circuit SC501 for voltage sampling in constant voltage application or current sampling in constant current application.

Hence, the power output module 407 is designed to receive the smart control scheme of the microcontroller 505, thus making the digital power converter in the embodiment fulfill the design of quasi-resonant soft switching in a half-bridge zero-voltage-switch (ZVS) way.

FIG. 6 is a schematic diagram of the high-power digital AC/DC power converter according to the embodiment of the present invention. The main difference between FIG. 6 and FIG. 5 is that the implementation of the power output module 607 in FIG. 6 is different from that of the power output module 507 in FIG. 5.

Referring to FIG. 6, the power output module 607 has four switches M601, M602, M603 and M604. The switches M601 and M502 are used to replace the capacitors C504 and C505 in FIG. 5. In the power output module 607, the switches M601 and M602 work in the same period of time and the switches M603, M604 work in another same period of time, respectively.

A microcontroller 605 controls an auxiliary IC 603 to output different rectangular pulses via Pins A1, A2, A3 and A4 to control the switches M601, M602, M603, M604, respectively, so that the switches M602 and M603 maintain in an OFF state when the switches M601 and M604 are switched to an ON state, and the switches M601 and M604 maintain in an OFF state when the switches M602 and M603 are switched to an ON state. Therefore, the switches: M601 and M604 and the switches: M602 and M603 operate alternatively in an opposite working state. Preferably, the switches M601, M602, M603 and M604 may be IGBT.

In the aforementioned power output module 607, a transformer TR includes a primary winding Np, a 1st secondary winding Ns1 and a 2nd secondary winding Ns2. The left side of the primary winding Np is electrically connected to the switches M601 and M602, and the right side of the primary winding Np is electrically connected to the switches M603 and M604. In addition, the right side of the primary winding Np is electrically connected to a capacitor C604 to isolate direct-current signal.

When the switches M601 and M604 are in an ON state and the switches M602 and M603 are in an OFF state, the voltage in the left side of the primary winding Np is higher than the voltage in the right side of the primary winding Np. Then, if the switches M601 and M604 are switched to an OFF state, the voltage in the left side of the primary winding Np will be lower than the voltage in the right side of the primary winding Np, and thus all the switches M601, M602, M603 and M604 are in an OFF state.

When all the switches M601, M602, M603 and M604 are in the OFF state, if the switches M602, M603 are switched to an ON state, the voltage in the left side of the primary winding Np will be changed to zero voltage and thus lower than the voltage in the right side of the primary winding Np, thus changing the direction of saving energy in the magnetic core of the transformer TR. Since the direction of magnetic lines inverses immediately in the aforementioned situation, the magnetic core is not easy to saturate, thus improving working efficiency, the operation rate of the magnetic core and the conversion rate of energy.

Then, when the switches M601 and M604 are in the OFF state and the switches M602 and M603 are in the ON state, if the switches M602 and M603 are switched to an OFF state, the switches M601 and M604 will be prepared to switch to an ON state after the switching of the switches M602 and M603. Therefore, a complete control cycle is achieved through the aforementioned switching process in FIG. 8.

Hence, the power output module 607 is designed to receive the smart control scheme of the microcontroller 605, thus making the digital power converter in the embodiment fulfill the design of quasi-resonant soft switching a full-bridge zero-voltage-switch (ZVS) way.

An at least 8-bit microprocessor (such as 16-bit, 32-bit . . . etc) may be adopted to be microcontrollers 305, 505 and 605 in the aforementioned embodiments, thus expanding at least 64 times the precision of the duty cycle of the amplified PWM signal Spwm to precisely control the increase or decrease of the duty cycle. For example, if the voltage of DC output is higher than a specific threshold (which can be defined as too high), the aforementioned microprocessor is able to control to decrease the duty cycle of Spwm, and if the voltage of DC output is lower than another specific threshold (which can be defined as too low), the aforementioned microprocessor is able to control to decrease the duty cycle of Spwm. Therefore, the expansion of the precision is achieved by software implementation in a digital microprocessor and hardware structure of the digital power converter, and thus the cost of the overall digital AC/DC power converter is down with a high-precision control of the duty cycle of PWM.

Previous descriptions are only embodiments of the present invention and are not intended to limit the scope of the present invention. Many variations and modifications according to the claims and specification of the disclosure are still within the scope of the claimed invention. In addition, each of the embodiments and claims does not have to achieve all the advantages or characteristics disclosed. Moreover, the abstract and the title only serve to facilitate searching patent documents and are not intended in any way to limit the scope of the claimed invention.

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23.0/100 Score

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69.81/100 Score

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48.0/100 Score

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Citation

Patents Cited in This Cited by
Title Current Assignee Application Date Publication Date
LLC controller with programmable fractional burst frequency POWER INTEGRATIONS, INC. 01 April 2011 04 October 2012
System and Method for Power Saving Conversion Topology in Switch Mode Power Supplies DELL PRODUCTS, LP 21 September 2007 26 March 2009
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